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1 ? fn7386.5 caution: these devices are sensitive to electrosta tic discharge; follow proper ic handling procedures. 1-888-intersil or 1-888-468-3774 | intersil (and design) is a registered trademark of intersil americas inc. copyright ? intersil americas inc. 2004, 2006, 2007. all rights reserved. all other trademarks mentioned are the property of their respective owners. el5156, el5157, el5256, el5257 <1mv voltage offset , 600mhz amplifiers the el5156, el5157, el5256, and el5257 are 600mhz bandwidth -3db voltage mode feedback amplifiers with dc accuracy of <0.01%, 1mv offsets and 40kv/v open loop gains. these amplifiers are i deally suited for applications ranging from precision measurement instrumentation to high speed video and monitor applications demanding the very highest linearity at very high frequency. capable of operating with as little as 6.0ma of curr ent from a single supply ranging from 5v to 12v and dual supplies ranging from 2.5v to 5.0v, these amplifiers are also well suited for handheld, portable and battery-powered equipment. with their capability to output as much as 140ma, any member of this family is comfortable with demanding load conditions. single amplifiers are available in sot-23 packages and duals in a 10 ld msop package for applications where board space is critical. additionally, singles and duals are available in the industry-standard 8 ld soic package. all parts operate over the industria l temperature range of -40c to +85c. features ? 600mhz -3db bandwidth, 240mhz 0.1db bandwidth ? 700v/s slew rate ? <1mv input offset ? very high open loop gains 92db ? low supply current = 6ma ? 140ma output current ? single supplies from 5v to 12v ? dual supplies from 2.5v to 5v ? fast disable on the el5156 and el5256 ?low cost ? pb-free available (rohs compliant) applications ?imaging ? instrumentation ?video ? communications devices pinouts el5156 (8 ld soic) top view el5157 (5 ld sot-23) top view el5256 (10 ld msop) top view el5257 (8 ld soic) top view 1 2 3 4 8 7 6 5 - + nc in- in+ vs- ce vs+ out nc 1 2 3 5 4 - + out vs- in+ vs+ in- 1 2 3 4 10 9 8 7 5 6 - + - + ina+ cea vs- ceb ina- outa vs+ outb inb+ inb- 1 2 3 4 8 7 6 5 - + - + outa ina- ina+ vs- vs+ outb inb- inb+ data sheet september 13, 2007
2 fn7386.5 september 13, 2007 ordering information part number part marking package pkg. dwg. # el5156is 5156is 8 ld soic (150 mil) mdp0027 el5156is-t7* 5156is 8 ld soic (150 mil) mdp0027 el5156is-t13* 5156is 8 ld soic (150 mil) mdp0027 el5156isz (note) 5156isz 8 ld soic (150 mil) (pb-free) mdp0027 el5156isz-t7* (note) 5156isz 8 ld soic (150 mil) (pb-free) mdp0027 el5156isz-t13* (note) 5156isz 8 ld soic (150 mil) (pb-free) mdp0027 el5157iw-t7* bhaa 5 ld sot-23 mdp0038 el5157iw-t7a* bhaa 5 ld sot-23 mdp0038 el5157iwz-t7* (note) baam 5 ld sot-23 (pb-free) mdp0038 el5157iwz-t7a* (note) baam 5 ld sot-23 (pb-free) mdp0038 el5256iy bahaa 10 ld msop (3.0mm) mdp0043 el5256iy-t7* bahaa 10 ld msop (3.0mm) mdp0043 EL5256IY-T13* bahaa 10 ld msop (3.0mm) mdp0043 el5257is 5257is 8 ld soic (150 mil) mdp0027 el5257is-t7* 5257is 8 ld soic (150 mil) mdp0027 el5257is-t13* 5257is 8 ld soic (150 mil) mdp0027 el5257iy bajaa 8 ld msop (3.0mm) mdp0043 el5257iy-t7* bajaa 8 ld msop (3.0mm) mdp0043 el5257iy-t13* bajaa 8 ld msop (3.0mm) mdp0043 *please refer to tb347 for detai ls on reel specifications. note: these intersil pb-free plastic packaged products employ special pb-free material sets; molding compounds/die attach materi als and 100% matte tin plate plus anneal - e3 terminatio n finish, which is rohs compliant and compat ible with both snpb and pb-free solderin g operations. intersil pb-free products are msl classified at pb-free peak reflow temperatures that meet or exceed the pb-free requirements o f ipc/jedec j std-020. el5156, el5157, el5256, el5257
3 fn7386.5 september 13, 2007 absolute maxi mum ratings (t a = +25c) thermal information supply voltage between v s and v s - . . . . . . . . . . . . . . . . . . . . 13.2v maximum slewrate from v s+ and v s - . . . . . . . . . . . . . . . . . . . 1v/s maximum continuous output current . . . . . . . . . . . . . . . . . . . 50ma current into i n +, i n -, ce . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 5ma pin voltages . . . . . . . . . . . . . . . . . . . . . . . . . gnd -0.5v to v s +0.5v junction temperature . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . +125c storage temperature . . . . . . . . . . . . . . . . . . . . . . . .-65c to +150c ambient operating temperature . . . . . . . . . . . . . . . .-40c to +85c power dissipation . . . . . . . . . . . . . . . . . . . . . . . . . . . . . see curves pb-free reflow profile . . . . . . . . . . . . . . . . . . . . . . . . . .see link below http://www.intersil.com/pbfree/pb-freereflow.asp caution: do not operate at or near the maximum ratings listed fo r extended periods of time. exposure to such conditions may adv ersely impact product reliability and result in failures not covered by warranty. important note: all parameters having min/max specifications are guaranteed. typical values are for information purposes only. u nless otherwise noted, all tests are at the specified temperature and are pulsed tests, therefore: t j = t c = t a electrical specifications v s + = +5v, v s - = -5v, ce = +5v, r f = r g = 562 , r l = 150 , t a = +25c, unless otherwise specified. parameter description conditions min (note 1) typ max (note 1) unit ac performance bw -3db bandwidth a v = +1, r l = 500 , c l = 4.7pf 600 mhz a v = +2, r l = 150 180 mhz gbwp gain bandwidth product r l = 150 210 mhz bw1 0.1db bandwidth a v = +2 70 mhz sr slew rate v o = -3.2v to +3.2v, a v = +2, r l = 150 500 640 v/s v o = -3.2v to +3.2v, a v = +1, r l = 500 700 v/s t s 0.1% settling time a v = +1 15 ns dg differential gain error a v = +2, r l = 150 0.005 % dp differential phase error a v = +2, r l = 150 0.04 v n input referred voltage noise 12 nv/ hz i n input referred current noise 5.5 pa/ hz dc performance v os offset voltage -1 0.5 1 mv t c v os input offset voltage temperature coefficient measured from t min to t max -3 v/c a vol open loop gain v o is from -2.5v to 2.5v 10 40 kv/v input characteristics cmir common mode input range guaranteed by cmrr test -2.5 +2.5 v cmrr common mode rejection ratio v cm = 2.5v to -2.5v 80 108 db i b input bias current el5156 and el5157 -1 -0.4 +1 a el5256 and el5257 -600 -200 +600 na i os input offset current -250 100 +250 na r in input resistance 10 25 m c in input capacitance 1pf output characteristics v out output voltage swing r l = 150 to gnd 3.4 3.6 v r l = 500 to gnd 3.6 3.8 v i out peak output current r l = 10 to gnd 80 140 ma el5156, el5157, el5256, el5257
4 fn7386.5 september 13, 2007 enable (el5156 and el5256 only) t en enable time 200 ns t dis disable time 300 ns i ihce ce pin input high current ce = v s +1325a i ilce ce pin input low current ce = v s -01a v ihce ce input high voltage for power-down v s + - 1 v v ilce ce input low voltage for power-up v s + - 3 v supply i son supply current - enabled (per amplifier) no load, v in = 0v, ce = +5v 5.1 6.0 6.9 ma i soff supply current - disabled (per amplifier) no load, v in = 0v, ce = 5v 5 13 25 a psrr power supply rejection ratio dc, v s = 3.0v to 6.0v 75 90 db note: 1. parts are 100% tested at +25c. over-temperature limits established by characterization and are not production tested. electrical specifications v s + = +5v, v s - = -5v, ce = +5v, r f = r g = 562 , r l = 150 , t a = +25c, unless otherwise specified. (continued) parameter description conditions min (note 1) typ max (note 1) unit typical performance curves figure 1. small signal frequency response - ga in figure 2. small signal frequency response - phase for various gains figure 3. small signal frequency response for various r l figure 4. small signal frequency response for various c l normalized gain (db) 4 frequency (hz) a v = +1 a v = +10 r l = 150 c l = 4.7pf 2 0 -2 -4 -6 100k 1m 10m 100m 1g a v = +5 a v = +2 r l = 150 c l = 4.7pf a v = +2 a v = +10 a v = +5 phase () 135 frequency (hz) 45 -45 -135 -225 -315 100k 1m 10m 100m 1g r l = 50 v s = 5v a v = +2 r f = r g = 562 r l = 750 r l = 150 r l = 500 normalized gain (db) 4 frequency (hz) 2 0 -2 -4 -6 100k 1m 10m 100m 1g a v = +1 r l = 500 c l = 27pf c l = 10pf c l = 4.7pf c l = 1pf gain (db) 5 frequency (hz) 3 1 -1 -3 -5 100k 1m 10m 100m 1g el5156, el5157, el5256, el5257
5 fn7386.5 september 13, 2007 figure 5. small signal frequency response for various c l figure 6. small signal frequency response for various c l figure 7. small signal frequency response for various c l figure 8. frequency response vs power supply figure 9. el5256 small signal frequency response for various gains figure 10. small signal inverting frequency response for various gains typical performance curves (continued) a v = +2 r l = 500 r f = r g = 500 c l = 22pf c l = 10pf c l = 0pf c l = 4.7pf normalized gain (db) 5 frequency (hz) 3 1 -1 -3 -5 100k 1m 10m 100m 1g c l = 8.2pf a v = +2 r l = 150 r f = r g = 562 c l = 180pf c l = 100pf c l = 33pf c l = 10pf c l = 0pf gain (db) 16 frequency (hz) 12 8 4 0 -4 100k 1m 10m 100m 1g a v = +5 r l = 500 c l = 100pf c l = 22pf c l = 68pf c l = 82pf normalized gain (db) 5 frequency (hz) 3 1 -1 -3 -5 100k 1m 10m 100m 1g a v = +1 r l = 500 c l = 4.7pf 2.0v 3.0v 4.0v 5.0v normalized gain (db) 5 frequency (hz) 3 1 -1 -3 -5 100k 1m 10m 100m 1g a v = +1 r l = 500 c l = 4.7pf a v = +1 a v = +5 a v = +2 normalized gain (db) 5 frequency (hz) 3 1 -1 -3 -5 100k 1m 10m 100m 1g v s = 5v r f = 620 r l = 150 a v = -1 a v = -2 normalized gain (db) 4 frequency (hz) 2 0 -2 -4 -6 100k 1m 10m 100m 1g el5156, el5157, el5256, el5257
6 fn7386.5 september 13, 2007 figure 11. small signal frequency response for various r l figure 12. el5256 small signal frequency response for various r l figure 13. small signal frequency response for various c in figure 14. small signal frequency response for various c in figure 15. small signal frequency response for various r f and r g figure 16. el5256 small signal frequency response for various r f and r g typical performance curves (continued) a v = +1 c l = 0.2pf r l = 300 r l = 150 r l = 500 normalized gain (db) 4 frequency (hz) 2 0 -2 -4 -6 100k 1m 10m 100m 1g a v = +1 c l = 4.7pf r l = 100 r l = 500 r l = 200 r l = 50 normalized gain (db) 5 frequency (hz) 3 1 -1 -3 -5 100k 1m 10m 100m 1g a v = +2 r l = 500 c l = 4.7pf r f = 500 c in = 12pf c in = 4.7pf c in = 0pf c in = 8.2pf c in = 0.2pf normalized gain (db) 5 frequency (hz) 3 1 -1 -3 -5 100k 1m 10m 100m a v = +5 c l = 4.7pf r l = 500 r f = 102 c in = 68pf c in = 0pf c in = 47pf c in = 22pf c in = 4.7pf normalized gain (db) 4 frequency (hz) 2 0 -2 -4 -6 100k 1m 10m 100m v s = 5v a v = +2 r l = 150 c l = 4.7pf normalized gain (db) 4 frequency (hz) 2 0 -2 -4 -6 100k 1m 10m 100m 1g r f = r g = 1k r f = r g = 350 r f = r g = 562 r f = r g = 500 r f = r g = 250 a v = +2 c l = 4.7pf r l = 500 r f = r g = 3k r f = r g = 2k r f = r g = 1k r f = r g = 500 r f = r g = 200 normalized gain (db) 6 frequency (hz) 4 2 0 -2 -4 100k 1m 10m 100m 1g el5156, el5157, el5256, el5257
7 fn7386.5 september 13, 2007 figure 17. large signal frequency response for various input amplitudes figure 18. channel to channel frequency response figure 19. el5256 crosstalk vs frequency channel a to b and b to a figure 20. bandwidth vs supply voltage figure 21. small signal frequency response for various r l figure 22. voltage and current noise vs frequency typical performance curves (continued) a v = +2 r l = 200 c l = 4.7pf -20dbm +10dbm +20dbm +15dbm +17dbm normalized gain (db) 5 frequency (hz) 3 1 -1 -3 -5 100k 1m 10m 100m 1g a v = +1 r l = 500 c l = 4.7pf ch1 ch2 normalized gain (db) 5 frequency (hz) 3 1 -1 -3 -5 100k 1m 10m 100m 1g a v = +5 r l = 500 c l = 4.7pf frequency (hz) 100k 1m 10m 100m 1g cross talk (10db) 0 -20 -40 -60 -80 -100 v s (v) 4.5 5.5 6.5 7.5 12.5 bw (mhz) 700 600 400 200 100 0 500 300 8.5 9.5 10.5 11.5 a v = +1, r l = 500 , c l = 5pf a v = +1, r l = 150 a v = +2, r l = 150 a v = +5 c l = 4.7pf r l = 1k r l = 500 r l = 100 r l = 50 normalized gain (db) 4 frequency (hz) 2 0 -2 -4 -6 100k 1m 10m 100m 1g v n i n voltage noise (nv/ hz), current noise (pa/ hz) 1k frequency (hz) 100 10 1 100k 1m 10m 100m 1g 10m 100m el5156, el5157, el5256, el5257
8 fn7386.5 september 13, 2007 figure 23. cmrr figure 24. output impedance figure 25. input to output isolation vs frequency - disable figure 26. supply current vs supply voltage figure 27. enable/disable response figure 28. peaking vs supply voltage typical performance curves (continued) cmrr (db) -20 frequency (hz) -40 -60 -120 100 1k 10k 1m 100m 100k 10m -80 -100 frequency (hz) 1k 10k 100k 10m 100m 1m a v = +2 r l = 0 r g = r f = 400 impedance ( ) 1k 100 10 0.01 1 v s = 5v a v = +2 r l = 150 frequency (hz) 100k 1m 10m 100m 1g disabled isolation (db) -10 -30 -50 -110 -70 -90 i s - i s + v s (v) 4.55.56.57.58.59.510.511.5 i s (ma) 6.1 6.0 5.9 5.3 5.5 5.4 5.6 5.8 5.7 time (400ns/div) enable 192ns a v = +2 r l = 500 supply = 5v 12.3ma disable 322ns a v = +1 c l = 5pf r l = 500 v s (v) 4.5 5.5 6.5 7.5 8.5 9.5 10.5 11.5 12.5 peaking (db) 0.8 0.7 0.6 0 0.2 0.1 0.3 0.5 0.4 el5156, el5157, el5256, el5257
9 fn7386.5 september 13, 2007 figure 29. small signal rise time figure 30. small signal fall time figure 31. large signal rise time figure 32. large signal fall time figure 33. package power dissipation vs ambient temperature figure 34. package power dissipation vs ambient temperature typical performance curves (continued) v out (40mv/div) time (4ns/div) rise 20% to 80% t = 2.025ns a v = +2 r l = 500 supply = 5v 12.3ma output = 200mv p-p 0 a v = +2 r l = 500 supply = 5v 12.3ma output = 200mv p-p fall 80% to 20% t = 1.7ns v out (40mv/div) time (4ns/div) 0 rise 20% to 80% t = 1.657ns a v = +2 r l = 500 supply = 5v 12.3ma output = 2.0v p-p v out (400mv/div) time (2ns/div) 0 a v = +2 r l = 500 supply = 5v 12.3ma output = 2.0v p-p fall 80% to 20% t = 1.7ns v out (400mv/div) time (2ns/div) 0 jedec jesd51-7 high effective thermal conductivity test board so8 ja = +110c/w 1.136w 543mw ambient temperature (c) 0 power dissipation (w) 0.2 0 0.6 0.4 1.0 0.8 1.4 1.2 1.8 1.6 25 75 85 100 125 150 50 870mw sot23-5 ja = +230c/w msop10 ja = +115c/w jedec jesd51-3 low effective thermal conductivity test board power dissipation (w) 0 0.6 0.2 0.8 0.4 1.2 1.0 ambient temperature (c) 0 25 75 85 100 125 150 50 so8 ja = +160c/w msop10 ja = +115c/w 781mw 488mw 486mw sot23-5 ja = +256c/w el5156, el5157, el5256, el5257
10 fn7386.5 september 13, 2007 el5156 product description the el5156, el5157, el5256, and el5257 are wide bandwidth, single or dual supply, low power and low offset voltage feedback operational amplifiers. both amplifiers are internally compensated for closed loop gain of +1 or greater. connected in voltage follower mode and driving a 500 load, the -3db bandwidth is about 610mhz. driving a 150 load and a gain of 2, the bandwidth is about 180mhz while maintaining a 600v/s slew rate. the el5156 and el5256 are available with a power-down pin to reduce power to 17a typically while the amplifier is disabled. input, output and supply voltage range the el5156 and el5157 families have been designed to operate with supply voltage from 5v to 12v. that means for single supply application, the supply voltage is from 5v to 12v. for split supplies application, the supply voltage is from 2.5v to 5v. the amplifiers have an input common mode voltage range from 1.5v above the negative supply (vs- pin) to 1.5v below the positive supply (vs+ pin). if the input signal is outside the above spec ified range, it will cause the output signal to be distorted. the outputs of the el5156 and el5157 families can swing from -4v to 4v for v s = 5v. as the load resistance becomes lower, the output swing is lower. if the load resistor is 500 , the output swing is about -4v at a 4v supply. if the load resistor is 150 , the output swing is from -3.5v to 3.5v. choice of feedback resistor and gain bandwidth product for applications that require a gain of +1, no feedback resistor is required. just shor t the output pin to the inverting input pin. for gains greater than +1, the feedback resistor forms a pole with the parasitic capacitance at the inverting input. as this pole becomes smaller, the amplifier's phase margin is reduced. this causes ringing in the time domain and peaking in the frequen cy domain. therefore, r f can't be very big for optimum performance. if a large value of r f must be used, a small capacitor in the few pico farad range in parallel with r f can help to reduce the ringing and peaking at the expense of reducing the bandwidth. for gain of +1, r f = 0 is optimum. for the gains other than +1, optimum response is obtained with r f between 500 to 750 . the el5156 and el5157 families have a gain bandwidth product of 210mhz. for gains 5, its bandwidth can be predicted by equation 1: video performance for good video performance, an amplifier is required to maintain the same output impedance and the same frequency response as dc levels are changed at the output. this is especially difficult when driving a standard video load of 150 , because of the change in output current with dc level. the dg and dp for thes e families are about 0.006% and 0.04%, while driving 150 at a gain of 2. driving high impedance loads would give a similar or better dg and dp performance. driving capacitive loads and cables the el5156 and el5157 families can drive 27pf loads in parallel with 500 with less than 5db of peaking at gain of +1. if less peaking is desired in applications, a small series resistor (usually between 5 to 50 ) can be placed in series with the output to eliminate most peaking. however, this will reduce the gain slightly. if the gain setting is greater than 1, the gain resistor r g can then be chosen to make up for any gain loss which may be created by the additional series resistor at the output. when used as a cable driver, double termination is always recommended for reflection-free performance. for those applications, a back-termination series resistor at the amplifier's output will isolate the amplifier from the cable and allow extensive capacitive drive. however, other applications may have high capacitive loads without a back-termination resistor. again, a small series resistor at the output can help to reduce peaking. disable/power-down the el5156 and el5256 can be disabled and their output placed in a high impedance state. the turn-off time is about 330ns and the turn-on time is about 130ns. when disabled, the amplifier's supply current is reduced to 17a typically, thereby effectively eliminating the power consumption. the amplifier's power-down can be controlled by standard ttl or cmos signal levels at the enable pin. the applied logic signal is relative to vs- pin. letting the enable pin float or applying a signal that is less than 0.8v above v s - will enable the amplifier. the amplifier will be disabled when the signal at enable pin is above v s + - 1.5v. output drive capability the el5156 and el5157 families do not have internal short circuit protection circuitry. they have a typical short circuit current of 95ma and 70ma. if the output is shorted indefinitely, the power dissipation could easily overheat the die or the current could eventually compromise metal integrity. maximum reliability is maintained if the output current never exceeds 40ma. this limit is set by the design of the internal metal interconnect. note that in transient applications, the part is robust. power dissipation with the high output drive capability of the el5152 and el5153 families, it is possible to exceed the +125c absolute maximum junction temperature under certain load current conditions. therefore, it is important to calculate the maximum junction temperature for an application to gain bw 210mhz = (eq. 1) el5156, el5157, el5256, el5257
11 fn7386.5 september 13, 2007 determine if load conditions or package types need to be modified to assure operation of the amplifier in a safe operating area. the maximum power dissipation allowed in a package is determined according to equation 2: where: t jmax = maximum junction temperature t amax = maximum ambi ent temperature ja = thermal resistance of the package the maximum power dissipation actually produced by an ic is the total quiescent supply current times the total power supply voltage, plus the power in the ic due to the load, or: for sourcing: for sinking: where: v s = supply voltage i smax = maximum quiescent supply current v out = maximum output voltage of the application r load = load resistance tied to ground i load = load current n = number of amplifiers (max = 2) by setting the two pd max equations equal to each other, we can solve the output current and r load to avoid the device overheat. power supply bypassing printed circuit board layout as with any high frequency device, a good printed circuit board layout is necessary for optimum performance. lead lengths should be as short as possible. the power supply pin must be well bypassed to reduce the risk of oscillation. for normal single supply operation, where the vs- pin is connected to the ground plane, a single 4.7f tantalum capacitor in parallel with a 0. 1f ceramic capacitor from vs+ to gnd will suffice. this same capacitor combination should be placed at each supply pin to ground if split supplies are to be used. in this case, the v s - pin becomes the negative supply rail. see figure 37 for a complete tuned power supply bypass methodology. printed circuit board layout for good ac performance, parasitic capacitance should be kept to a minimum. use of wire wound resistors should be avoided because of their additional series inductance. use of sockets should also be avoided if possible. sockets add parasitic inductance and capacitance that can result in compromised performance. minimizing parasitic capacitance at the amplifier's inverting in put pin is very important. the feedback resistor should be placed very close to the inverting input pin. strip line design techniques are recommended for the signal traces. pd max t jmax t amax ? ja -------------------------------------------- - = (eq. 2) pd max v s i smax v s v outi ? () i1 = n v outi r li ----------------- + = (eq. 3) pd max v s i smax v outi v s ? () i1 = n i loadi + = (eq. 4) el5156, el5157, el5256, el5257
12 fn7386.5 september 13, 2007 application circuits sallen key low pass filter a common and easy to implemen t filter taking advantage of the wide bandwidth, low offset and low power demands of the el5152. a derivation of th e transfer function is provided for convenience (see figure 35). sallen key high pass filter again this useful filter benefits from the characteristics of the el5152. the transfer function is very similar to the low pass so only the results are presented (see figure 36). figure 35. sallen key low pass filter equations simplify if we let all components be equal to r = c + - v+ v- v 2 5v l 1 10h l 1 10h r 6 1k c 5 1nf c 4 1nf v out r 7 1k v 3 5v r 1 1k r 2 1k c 2 1nf v 1 c 1 1nf c 5 1nf r 5 1k c 3 1nf r a 1k r b 1k tuned power bypass network tuned power bypass network k1 r b r a ------- - + = v o k 1 r 2 c 2s 1 + ? -------------------------------- - v o ?? = v 1 v i ? r 1 ------------------ 1 v o kv 1 ? ---------------- - r 2 ---------------- - v o v i ? 1 c 1s ---------- - ------------------- 0 = ++ hjw ?? 1 1w 2 r 1 c 1 r 2 c 2 ? jw 1 k ? () r 1 c 1 r 1 c 2 r 2 c 2 ++ () + ------------------------------------------------------------------------------------------------------------------------------- ---------------- - = hs ?? k r 1 c 1 r 2 c 2s 2 1k ? () r 1 c 1 r 1 c 2 r 21 c 2 ++ () s1 ++ ------------------------------------------------------------------------------------------------------------------------------- --------------- - = holp k = wo 1 r 1 c 1 r 2 c 2 ---------------------------------- - = q 1 1k ? ?? r 1 c 1 r 2 c 2 -------------- - r 1 c 2 r 2 c 1 -------------- - r 2 c 2 r 1 c 1 -------------- - ++ ------------------------------------------------------------------------------------------- - = holp k = wo 1 rc -------- - = q 1 3k ? ------------ - = el5156, el5157, el5256, el5257
13 fn7386.5 september 13, 2007 differential output instrumentation amplifier the addition of a third amplifier to the conventional three amplifier instrumentation amplif ier introduces the benefits of differential signal realization, specifically the advantage of using common mode rejection to remove coupled noise and ground potential errors inherent in remote transmission. this configuration also provides enhanced bandwidth, wider output swing and faster slew rate than conventional three amplifier solutions with only the cost of an additional amplifier and a few resistors. figure 36. sallen key high pass filter equations simplify if we let all components be equal to r = c + - v+ v- v 2 5v l 1 10h l 1 10h r 6 1k c 5 1nf c 4 1nf v out r 7 1k v 3 5v r 1 1k r 2 1k c 2 1nf v 1 c 1 1nf c 5 1nf r 5 1k c 3 1nf r a 1k r b 1k tuned power bypass network tuned power bypass network wo 1 r 1 c 1 r 2 c 2 ----------------------------------- = q 1 1k ? ?? r 1 c 1 r 2 c 2 -------------- - r 1 c 2 r 2 c 1 -------------- - r 2 c 2 r 1 c 1 -------------- - ++ ------------------------------------------------------------------------------------------- - = holp k = holp k 4k ? ------------ - = wo 2 rc -------- - = q 2 4k ? ------------ - = + - - + - + + - e o e o 4 e o 3 ref r 3 r 3 r 3 r 3 r 3 r 3 r 2 r 2 r g a 2 e 2 a 4 a 3 r 3 r 3 a 1 e 1 + - e o3 12r 2 r g ? + () e 1 e 2 ? () ? = e o4 12r 2 r g ? + () e 1 e 2 ? () = e o 21 2r 2 r g ? + () e 1 e 2 ? () ? = bw 2f c1 2 , a di ----------------- - = a di 21 2r 2 r g ? + () ? = el5156, el5157, el5256, el5257
14 fn7386.5 september 13, 2007 strain gauge the strain gauge is an ideal application to take advantage of the moderate bandwidth and hi gh accuracy of the el5152. the operation of the circuit is very straightforward. as the strain variable component resistor in the balanced bridge is subjected to increasing strain, its resistance changes, resulting in an imbalance in the bridge. a voltage variation from the referenced high accuracy source is generated and translated to the difference amplifier through the buffer stage. this voltage difference as a function of the strain is converted into an output voltage. figure 37. strain gauge operational circuit el5156, el5157, el5256, el5257
15 fn7386.5 september 13, 2007 el5156, el5157, el5256, el5257 small outline package family (so) gauge plane a2 a1 l l1 detail x 4 4 seating plane e h b c 0.010 b m ca 0.004 c 0.010 b m ca b d (n/2) 1 e1 e n n (n/2)+1 a pin #1 i.d. mark h x 45 a see detail ?x? c 0.010 mdp0027 small outline package family (so) symbol inches tolerance notes so-8 so-14 so16 (0.150?) so16 (0.300?) (sol-16) so20 (sol-20) so24 (sol-24) so28 (sol-28) a 0.068 0.068 0.068 0.104 0.104 0.104 0.104 max - a1 0.006 0.006 0.006 0.007 0.007 0.007 0.007 0.003 - a2 0.057 0.057 0.057 0.092 0.092 0.092 0.092 0.002 - b 0.017 0.017 0.017 0.017 0.017 0.017 0.017 0.003 - c 0.009 0.009 0.009 0.011 0.011 0.011 0.011 0.001 - d 0.193 0.341 0.390 0.406 0.504 0.606 0.704 0.004 1, 3 e 0.236 0.236 0.236 0.406 0.406 0.406 0.406 0.008 - e1 0.154 0.154 0.154 0.295 0.295 0.295 0.295 0.004 2, 3 e 0.050 0.050 0.050 0.050 0.050 0.050 0.050 basic - l 0.025 0.025 0.025 0.030 0.030 0.030 0.030 0.009 - l1 0.041 0.041 0.041 0.056 0.056 0.056 0.056 basic - h 0.013 0.013 0.013 0.020 0.020 0.020 0.020 reference - n 8 14 16 16 20 24 28 reference - rev. m 2/07 notes: 1. plastic or metal protrusions of 0.006? maximum per side are not included. 2. plastic interlead protrusions of 0.010? maximum per side are not included. 3. dimensions ?d? and ?e1? are measured at datum plane ?h?. 4. dimensioning and tolerancing per asme y14.5m - 1994
16 fn7386.5 september 13, 2007 el5156, el5157, el5256, el5257 sot-23 package family e1 n a d e 4 3 2 1 e1 0.15 d c 2x 0.20 c 2x e b 0.20 m d c a-b b nx 6 2 3 5 seating plane 0.10 c nx 1 3 c d 0.15 a-b c 2x a2 a1 h c (l1) l 0.25 0 +3 -0 gauge plane a mdp0038 sot-23 package family symbol millimeters tolerance sot23-5 sot23-6 a 1.45 1.45 max a1 0.10 0.10 0.05 a2 1.14 1.14 0.15 b 0.40 0.40 0.05 c 0.14 0.14 0.06 d 2.90 2.90 basic e 2.80 2.80 basic e1 1.60 1.60 basic e 0.95 0.95 basic e1 1.90 1.90 basic l 0.45 0.45 0.10 l1 0.60 0.60 reference n 5 6 reference rev. f 2/07 notes: 1. plastic or metal protrusions of 0.25mm maximum per side are not included. 2. plastic interlead protrusions of 0.25mm maximum per side are not included. 3. this dimension is measured at datum plane ?h?. 4. dimensioning and tolerancing per asme y14.5m-1994. 5. index area - pin #1 i.d. will be located within the indicated zone (sot23-6 only). 6. sot23-5 version has no center lead (shown as a dashed line).
17 all intersil u.s. products are manufactured, asse mbled and tested utilizing iso9000 quality systems. intersil corporation?s quality certifications ca n be viewed at www.intersil.com/design/quality intersil products are sold by description only. intersil corpor ation reserves the right to make changes in circuit design, soft ware and/or specifications at any time without notice. accordingly, the reader is cautioned to verify that data sheets are current before placing orders. information furnishe d by intersil is believed to be accurate and reliable. however, no responsibility is assumed by intersil or its subsidiaries for its use; nor for any infringements of paten ts or other rights of third parties which may result from its use. no license is granted by implication or otherwise under any patent or patent rights of intersil or its subsidiari es. for information regarding intersil corporation and its products, see www.intersil.com fn7386.5 september 13, 2007 el5156, el5157, el5256, el5257 mini so package family (msop) 1 (n/2) (n/2)+1 n plane seating n leads 0.10 c pin #1 i.d. e1 e b detail x 3 3 gauge plane see detail "x" c a 0.25 a2 a1 l 0.25 c a b d a m b e c 0.08 c a b m h l1 mdp0043 mini so package family symbol millimeters tolerance notes msop8 msop10 a1.101.10 max. - a1 0.10 0.10 0.05 - a2 0.86 0.86 0.09 - b 0.33 0.23 +0.07/-0.08 - c0.180.18 0.05 - d 3.00 3.00 0.10 1, 3 e4.904.90 0.15 - e1 3.00 3.00 0.10 2, 3 e0.650.50 basic - l0.550.55 0.15 - l1 0.95 0.95 basic - n 8 10 reference - rev. d 2/07 notes: 1. plastic or metal protrusions of 0.15mm maximum per side are not included. 2. plastic interlead protrusions of 0.25mm maximum per side are not included. 3. dimensions ?d? and ?e1? are measured at datum plane ?h?. 4. dimensioning and tolerancing per asme y14.5m-1994.

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